Impedance Matching Device and Impedance Matching Method

ABSTRACT

An impedance matching device comprises a variable capacitor including multiple capacitance elements and connected in parallel having capacitors and each having one end connected in series to a high-frequency power source and semiconductor switches and connected to the respective capacitors, and a control unit. The control unit derives a reflection coefficient based on the obtained information concerning an impedance viewed from the high-frequency power source toward the load side, updates the states of the respective semiconductor switches and included in the multiple capacitance elements and with a first cycle in the case where the reflection coefficient is equal to or more than a predetermined value, and updates the states of the respective semiconductor switches and included in the plurality of capacitance elements and with a second cycle longer than the first cycle in the case where the reflection coefficient is less than the predetermined value.

CROSS-REFERENCE TO RELATED APPLICATION

This Non-provisional application claims priority under 35 U.S.C § 119(a)on Patent Application No. 2018-243192 filed in Japan on Dec. 26, 2018,the entire contents of which are hereby incorporated by reference.

FILED

The present disclosure relates to an impedance matching device and animpedance matching method that achieve impedance matching between ahigh-frequency power source and a load.

BACKGROUND

An impedance matching device has been known that matches an outputimpedance of a high-frequency power source to an impedance viewed fromthe high-frequency power source toward a load side in order to eliminatereflected power from a load and efficiently supply power to the loadwhen power is supplied from the high-frequency power source to the loadsuch as a plasma load or the like (for example, refer to Japanese Patentapplication Laid-Open No. 2012-142285 as Patent Document 1).

The impedance matching device disclosed in Patent Document 1 includes avariable capacitor, and is provided between a high-frequency powersource and a load. The variable capacitor disclosed in Patent Document 1includes multiple capacitors connected in parallel to each other, and isconfigured to change the capacitance of the variable capacitor byperforming switching control of turning on or off semiconductor switches(PIN diodes) connected in series to the respective capacitors. Theimpedance matching device disclosed in Patent Document 1 achievesimpedance matching by changing the capacitance of the variablecapacitor.

SUMMARY

However, in the case where high-frequency power is supplied to a loadwhose impedance frequently varies such as a plasma load, continuousupdating of the states of the semiconductor switches for deciding thecapacitance of the variable capacitor following the variation in theload impedance results in fast and continuous on-off operation of thesemiconductor switches.

This operation raises a problem of increase in the amount of heatgenerated in the semiconductor switches due to switching loss.

It is an object of the present disclosure to provide an impedancematching device and an impedance matching method that are able to reducethe amount of heat generated in the semiconductor switches.

An impedance matching device according to one aspect of the presentdisclosure is an impedance matching device that is provided between ahigh-frequency power source and a load, and that obtains informationconcerning an impedance viewed from an output terminal of thehigh-frequency power source or from its equivalent to the outputterminal toward a load side to thereby achieve impedance matchingbetween the high-frequency power source and the load. The impedancematching device comprises: a variable capacitor including a plurality ofcapacitance elements respectively having capacitor each having one endconnected to the high-frequency power source and semiconductor switchconnected in series to the capacitor, the plurality of capacitanceelements being connected in parallel; and a control unit that controlsan on or off state of the semiconductor switches such that an impedanceof the high-frequency power source is matched to an impedance of theload based on the information concerning the impedance obtained, and thecontrol unit derives a reflection coefficient based on the informationobtained concerning the impedance viewed from the high-frequency powersource toward the load side, updates states of the respectivesemiconductor switches included in the plurality of capacitance elementswith a first cycle in the case where the reflection coefficient is equalto or more than a predetermined value, and updates states of therespective semiconductor switches included in the plurality ofcapacitance elements with a second cycle longer than the first cycle inthe case where the reflection coefficient is less than the predeterminedvalue. Here, the part equivalent to the output terminal is the inputterminal of the impedance matching device, for example.

According to the present aspect, the control unit updates the states ofthe respective semiconductor switches included in the plurality ofcapacitance elements with the first cycle in the case where thereflection coefficient is equal to or more than the predetermined valuewhereas the control unit updates the states of the respectivesemiconductor switches included in the plurality of capacitance elementswith the second cycle longer than the first cycle in the case where thereflection coefficient is less than the predetermined value.Accordingly, after the reflection coefficient is less than thepredetermined value, i.e., in a near-matched state, precise adjustmentis required. However, updating with the second cycle that is longer thanthe first cycle can reduce the switching counts of the semiconductorswitches, which reduces the heat generation.

In the impedance matching device according to one aspect of the presentdisclosure, the predetermined value for the reflection coefficient is0.1.

According to the present aspect, the predetermined value for thereflection coefficient is set to 0.1, so that the value can be used as athreshold for determining whether or not a matched state is almostachieved.

In the impedance matching device according to one aspect of the presentdisclosure, the plurality of capacitance elements include a firstcapacitance element group and a second capacitance element group thatincludes the capacitors each having a capacitance smaller than acapacitance of one of the capacitors constituting the first capacitanceelement group, and the control unit updates states of the semiconductorswitches included in the first capacitance element group and maintainsstates of the semiconductor switches included in the second capacitanceelement group at a time of updating with the first cycle, and updatesstates of the semiconductor switches included in the first capacitanceelement group and the semiconductor switches included in the secondcapacitance element group at a time of updating with the second cycle.

According to the present aspect, the plurality of capacitance elementsinclude a first capacitance element group and a second capacitanceelement group that includes the capacitors each having a capacitancesmaller than a capacitance of one of the capacitors constituting thefirst capacitance element group. The control unit updates the states ofthe semiconductor switches included in the first capacitance elementgroup at a time of updating with the first cycle whereas the controlunit updates the states of the semiconductor switches included in thefirst capacitance element group and the semiconductor switches includedin the second capacitance element group at a time of updating with thesecond cycle. The first capacitance element group includes thecapacitors each having a large capacitance, so that change of onecapacitance causes great change in the impedance. Accordingly, duringthe unmatched state where the reflection coefficient is equal to or morethan a predetermined value, rough adjustments are performed, so that animpedance is first adjusted by the first capacitance element group. Ifthe reflection coefficient is less than the predetermined value (in thenear-matched state), precise adjustments are required, so that thesecond capacitance element group is added to thereby adjust theimpedance using the first capacitance element group and the secondcapacitance element group. The capacitors of the second capacitanceelement group having smaller capacitances than those of the capacitorsconstituting the first capacitance element group frequently repeatswitching (updating the states of the semiconductor switches). Thecapacitor with particularly smaller capacitance performs switchinghighly frequently.

In contrast thereto, in the case of the unmatched state where thereflection coefficient is equal to or more than the predetermined value,the first capacitance element group is switched with the first cyclewhile in the case where the reflection coefficient is less than thepredetermined value (in the near-matched state), the first capacitanceelement group and the second capacitance element group are switched withthe second cycle, thereby updating the states of the semiconductorswitches.

The second cycle is set to an cycle longer than the first cycle. Hence,if the reflection coefficient is less than the predetermined value (inthe near-matched state), the update cycle is extended to thereby reducethe heat generation caused by the switching of the second capacitanceelement group. It is noted that after the near-matched state, the stateof the first capacitance element group is scarcely changed, whichlessens the influence of the heat generation due to the switching of thefirst capacitance element group.

That is, in the case where the reflection coefficient is less than thepredetermined value (in the near-matched state), the update cycle isextended to thereby reduce the switching loss caused by thesemiconductor switches being turned on or off, preventing thetemperatures of the semiconductor switches from rising. In contrast, inthe case of the unmatched state where the reflection coefficient is morethan the predetermined value, the semiconductor switches of the firstcapacitance element group including the capacitors with largecapacitances are updated with the first cycle, and thus the targetedimpedance matching point can be reached soon.

In the impedance matching device according to one aspect of the presentdisclosure, a capacitance of any one of the capacitors included in thefirst capacitance element group is larger than a total value ofcapacitances of all the capacitors included in the second capacitanceelement group.

According to the present aspect, the capacitance of any one of thecapacitors included in the first capacitance element group is largerthan the total value of the capacitances of all the capacitors includedin the second capacitance element group. Accordingly, if the capacitancerequired for the variable capacitor is larger than the total value ofthe capacitance of all the capacitors included in the second capacitanceelement group, this can be addressed by using the capacitors included inthe first capacitance element group.

An impedance matching method according to one aspect of the presentdisclosure is for achieving impedance matching between a high-frequencypower source and a load by a variable capacitor provided between thehigh-frequency power source and the load. The variable capacitorincludes a plurality of capacitance elements having respectivecapacitors and respective semiconductor switches, and the methodcomprises: deriving a reflection coefficient based on informationobtained concerning an impedance viewed from the high-frequency powersource toward a load side; updating states of the respectivesemiconductor switches included in the plurality of capacitance elementswith a first cycle in the case where the reflection coefficient is equalto or more than a predetermined value; and updating states of therespective semiconductor switches included in the plurality ofcapacitance elements with a second cycle longer than the first cycle inthe case where the reflection coefficient is less than the predeterminedvalue.

According to the present aspect, it is possible to provide the impedancematching method capable of reducing the amount of heat generated in thesemiconductor switches.

It is possible to provide an impedance matching device and an impedancematching method that are able to reduce the amount of heat generated inthe semiconductor switches.

The above and further objects and features will more fully be apparentfrom the following detailed description with accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a circuit diagram roughly illustrating one example of theconfiguration of an impedance matching device according to Embodiment 1.

FIG. 2 is a block diagram roughly illustrating one example of theconfiguration of a control unit.

FIG. 3 is a circuit diagram roughly illustrating one example of theconfiguration of a driving circuit.

FIG. 4 is an illustrative view of a first capacitance element group.

FIG. 5 is an illustrative view of a second capacitance element group.

FIG. 6 is an illustrative view of an update cycle of semiconductorswitches.

FIG. 7 is a flowchart illustrating processing performed by the controlunit according to Embodiment 1.

FIG. 8 is a circuit diagram illustrating one example of theconfiguration of a driving circuit according to Modification 1.

MODE FOR CARRYING OUT DISCLOSURE Embodiment 1

The present disclosure will be described below with reference to thedrawings depicting embodiments thereof. FIG. 1 is a circuit diagramroughly illustrating one example of the configuration of an impedancematching device 1 according to Embodiment 1. The impedance matchingdevice 1 is connected between a high-frequency power source 6 and a load8. Between the high-frequency power source 6 and the impedance matchingdevice 1, a high-frequency detection unit 7 is provided. That is, thehigh-frequency detection unit 7 is provided between the output terminalof the high-frequency power source 6 and the input terminal of theimpedance matching device 1. The impedance matching device 1 obtainsinformation concerning an impedance (load-side impedance) viewed fromthe high-frequency power source 6 toward the load 8 side that isdetected by the high-frequency detection unit 7, and matches theimpedance viewed from the high-frequency power source 6 toward the load8 side to the output impedance of the high-frequency power source 6(makes the load-side impedance and the output impedance of thehigh-frequency power source 6 conjugate with each other) based on theinformation.

The high-frequency power source 6 is an alternating current (AC) powersource that outputs high-frequency power at the radio frequency (RF)band, for example, of 2 MHz, 13.56 MHz, 27 MHz or 60 MHz or the like,and has an output impedance set to a predetermined value such as 50Ω,for example. The high-frequency power source 6 includes an invertercircuit (not illustrated), and performs switching control of theinverter circuit at high speeds to thereby generate AC power at highfrequencies and outputs the generated AC power to the load 8.

The load 8 is for performing various processing using the high-frequencypower input from the high-frequency power source 6 and includes, forexample, a plasma processing apparatus, contactless power transferdevice, or the like. In the plasma processing apparatus, the state ofthe plasma varies with time as the manufacturing process such as plasmaetching, plasma CVD, etc. advances. This varies the impedance of theload 8. In order to efficiently supply power to the load 8 from thehigh-frequency power source 6, the impedance (load-side impedance)viewed from the high-frequency power source 6 toward the load 8 sideneeds to be adjusted as the impedance of the load 8 varies.

The high-frequency detection unit 7 detects parameters used forcalculating the load-side impedance, which is an impedance viewed fromthe output terminal of the high-frequency power source 6 toward the load8 side. The parameters are derived using high-frequency voltage andhigh-frequency current that are supplied from the high-frequency powersource 6 to the load 8 as well as a phase difference between thehigh-frequency voltage and the high-frequency current, for example. Theparameters include forward wave voltage, reflected wave voltage, forwardwave current, reflected wave current, forward wave power and reflectedwave power that are detected at the connection node between thehigh-frequency detection unit 7 and the impedance matching device 1 orat the output terminal of the high-frequency power source 6, or includea reflection coefficient derived by using the forward wave voltage, etc.and the reflected wave voltage, etc. The matter concerning thereflection coefficient is based on a known art (Japanese PatentApplication Laid-Open No. 2014-236435), for example. The parametersinclude transmission parameters (T parameters) or scattering parameters(S parameters) as disclosed in a known document (Japanese PatentApplication Laid-Open No. 2006-166412). The high-frequency detectionunit 7 corresponds to an impedance detection unit that detectsinformation concerning the impedance (load-side impedance) viewed fromthe high-frequency power source 6 toward the load 8 side. Note that theload-side impedance corresponds to a complex impedance of the impedanceof the load 8 and the impedance of the impedance matching device 1, andthus the impedance of the load 8 may be derived by subtracting theimpedance of the impedance matching device 1 from the load-sideimpedance.

The impedance matching device 1 includes two variable capacitors 2, aninductor 5, driving circuits 3 and a control unit 4. The impedancematching device 1 changes the capacitance of the variable capacitors 2based on the information concerning the load-side impedance detected bythe high-frequency detection unit 7 and adjusts the load-side impedance,to thereby achieve impedance matching. Moreover, the impedance matchingdevice 1 derives a reflection coefficient based on the informationconcerning the load-side impedance detected by the high-frequencydetection unit 7 and controls update cycles of the variable capacitors 2based on the derived reflection coefficient.

In the impedance matching device 1, one of the variable capacitors 2 hasone end connected to the high-frequency power source 6 via thehigh-frequency detection unit 7 and the other end connected to theground (grounded). The other one of the variable capacitor 2 isconnected to the one variable capacitor 2 in parallel and has one endconnected to the high-frequency power source 6 via the high-frequencydetection unit 7 and the other end connected to the load 8. Between theother variable capacitor 2 and the load 8, the inductor 5 is connectedin series. That is, the connection between the variable capacitor 2 andthe high-frequency power source 6 is not limited to the directconnection and includes indirect connection via the high-frequencydetection unit 7 or the like as well. These two variable capacitors 2and the inductor 5 constitute a reverse L-shaped matching circuit 11.Note that the matching circuit 11 may be, though not limited to thereverse L-shaped matching circuit 11, a π typed matching circuit 11 inwhich two variable capacitors 2 each having one end connected to thehigh-frequency power source 6 and the other end connected to the ground(grounded) are provided so as to be connected in parallel.

The variable capacitors 2 each include a first capacitance element group21 and a second capacitance element group 22. The first capacitanceelement group 21 includes multiple first capacitance elements 211 thatare connected in parallel to each other. The first capacitance elements211 each include a higher-order bit capacitor 212 that has one endconnected to the high-frequency power source 6 side and a higher-orderbit switch 213 that is connected in series to the other end of thehigher-order bit capacitor 212. The capacitances of the respectivehigher-order bit capacitors 212 are set to the same.

The higher-order bit switch 213 is, for example, a PIN diode having theanode connected to the high-frequency power source 6 side and thecathode connected to the ground side. To the connection node between theanode of the PIN diode and the other end of the higher-order bitcapacitor 212, an electric wire to which DC voltage from the drivingcircuit 3 as described below is output is connected. The DC voltageoutput from the driving circuit 3 is applied in a forward directionbetween the anode and the cathode of the PIN diode, to thereby turn thePIN diode to the on state. The higher-order bit switch 213 formed by thePIN diode is turned to the on state, to thereby allow high-frequencycurrent to bidirectionally flow through the higher-order bit switch 213.Furthermore, the higher-order bit switch 213 is turned to the on stateto thereby allow the higher-order bit capacitor 212 connected in seriesto the higher-order bit switch 213 to work. Depending on the number ofhigher-order bit switches 213 that are turned to the on state, thecapacitance of the first capacitance element group 21 (the capacitanceof the single higher-order bit capacitor 212*the number of higher-orderbit switches 213 that are turned to the on state) can be adjusted.

The second capacitance element group 22 includes multiple secondcapacitance elements 221 that are connected in parallel to each other.The second capacitance elements 221 each include a lower-order bitcapacitor 222 having one end connected to the high-frequency powersource 6 side and a lower-order bit switch 223 connected in series tothe other end of the lower-order bit capacitor 222.

The capacitances of the respective lower-order bit capacitors 212 areset to be different from each other in a stepwise manner. Out of thelower-order bit capacitors 222, the lower-order bit capacitors 222 otherthan the lower-order bit capacitor 222 with the smallest capacitance(the smallest capacitor) are set to values obtained by multiplying thecapacitance of the smallest capacitor by powers of two. The details ofthe relationship between the capacitances of the respective lower-orderbit capacitors 222 and the capacitances of the higher-order bitcapacitors 212 or the like will be described later.

Similarly to the higher-order bit switch 213, the lower-order bit switch223 is a PIN diode having the anode connected to the high-frequencypower source 6 side and the cathode connected to the ground side, and isturned to the on state in response to the DC voltage output from thedriving circuit 3. The lower-order bit switch 223 is turned to the onstate to thereby allow the lower-order bit capacitor 222 connected inseries to the lower-order bit switch 223 to work. Depending on thestates of the lower-order bit switches 223 that are turned to the onstate, the capacitance of the second capacitance element group 22 (thetotal value of the capacitances of the lower-order bit capacitors 222that are turned to the on state) can be adjusted.

It is noted that in the present embodiment, three first capacitanceelements 211 included in the first capacitance element group 21 areprovided while four second capacitance elements 221 included in thesecond capacitance element group 22 are provided. The number ofcapacitance elements may however take any number, not limited to theabove. In some embodiments, two or more first capacitance elements 211may be provided while two or more second capacitance elements 221 may beprovided. In FIG. 1, the variable capacitor 2 is constituted by, thoughnot limited to, the first capacitance element group 21 and the secondcapacitance element group 22. The variable capacitor 2 may include acapacitance element other than the first capacitance element group 21and the second capacitance element group 22. In FIG. 1, the impedancematching device 1 is configured to include two variable capacitors 2 inorder to adjust the capacitance though the number of variable capacitors2 may however take any number, not limited to the above. The impedancematching device 1 may include one, or three or more variable capacitors2 and further include a capacitor with a fixed capacitance, in order toadjust the capacitance.

FIG. 2 is a block diagram roughly illustrating one example of theconfiguration of the control unit 4. The control unit 4 is constitutedby a central processing unit (CPU), a micro processing unit (MPU) or thelike, and has a clock function and a calculation function. The controlunit 4 is connected to a storage unit 40 such as a read only memory(ROM), a random access memory (RAM) or the like through an internal busor the like, and executes a program stored in the storage unit 40 tothereby function as an impedance calculation unit 41, a capacitancecalculation unit 42, a targeted switch-state decision unit 43 and anupdate cycle decision unit 44. The control unit 4, which includes aswitch control unit 45, obtains information concerning the impedance(load-side impedance) viewed from the high-frequency power source 6toward the load 8 side that is detected by the high-frequency detectionunit 7 and controls the switch control unit 45 based on the informationto thereby adjust the capacitance of the variable capacitor 2, achievingthe impedance matching.

The impedance calculation unit 41 is a function unit for obtaininginformation concerning the impedance viewed from the high-frequencypower source 6 toward the load 8 side that is detected and output by thehigh-frequency detection unit 7 or the parameters including theinformation at a predetermined cycle to thereby calculate the impedanceviewed from the high-frequency power source 6 toward the load 8 side asload-side impedance. The cycle (calculation cycle) for calculating theload-side impedance is, for example, 100 μsec to 1 msec. Moreover, theimpedance calculation unit 41 obtains information concerning theimpedance viewed from the high-frequency power source 6 toward the load8 side that is detected and output by the high-frequency detection unit7 or the parameters including the information at predetermined cycles,and derives a reflection coefficient. As described above, the parametersdetected by the high-frequency detection unit 7 include the reflectioncoefficient, and thus the impedance calculation unit 41 may derive thereflection coefficient from the parameters obtained from thehigh-frequency detection unit 7. Alternatively, the impedancecalculation unit 41 may calculate the reflection coefficient (reflectioncoefficient=reflected wave voltage/forward wave voltage) based on theforward wave voltage, the reflected wave voltage, etc. included in theparameters. That is, the impedance calculation unit 41 corresponds to areflection coefficient derivation unit.

The capacitance calculation unit 42 is a function unit for calculatingthe capacitance required for the variable capacitor 2 in order to matchthe load-side impedance calculated by the impedance calculation unit 41to the output impedance of the high-frequency power source 6.

The targeted switch-state decision unit 43 is a function unit fordeciding the on or off state of the respective PIN diodes (thehigher-order bit switch 213 or the lower-order bit switch 223, or thehigher-order bit switch 213 and the lower-order bit switch 223) includedin the variable capacitor 2 in order to match the capacitance of thevariable capacitor 2 to the capacitance calculated by the capacitancecalculation unit 42.

The update cycle decision unit 44 is a function unit for obtaining areflection coefficient derived by the impedance calculation unit 41 anddeciding the cycle (update cycle) to update the state of thehigher-order bit switch 213 or the lower-order bit switch 223 based onthe reflection coefficient. The update cycle is, for example, 100 μsecto 5 msec, and the update cycle may be equalized with the load-sideimpedance calculation cycle or the reflection coefficient derivationcycle (calculation cycle). The details of the update cycle decision unit44 will be described later using the flowchart, which will be describedlater.

The switch control unit 45 includes a control circuit 451 and a branchcircuit 452 (see FIG. 3). The switch control unit 45 updates the stateof the higher-order bit switch 213 or the lower order bit switch 223, orthe states of the higher-order bit switch 213 and the lower-order bitswitch 223 at the update cycle decided by the update cycle decision unit44. The switch control unit 45 outputs to the driving circuit 3 anon-off signal for updating the state of the higher-order bit switches213 or the lower-order bit switches 223 based on the state of thehigher-order bit switch 213 or the lower-order bit switch 223 decided bythe targeted switch-state decision unit 43, and updates the state of thehigher-order bit switch 213 or the lower-order bit switch 223.

FIG. 3 is a circuit diagram roughly illustrating one example of theconfiguration of the driving circuit 3. The driving circuit 3 isprovided for each of the higher-order bit switches 213 or each of thelower-order bit switches 223 as illustrated in FIG. 1. It is noted thatFIG. 3 mainly illustrates the first capacitance element 211.

The one end of the driving circuit 3 is connected to the connection nodebetween the higher-order bit capacitor 212 or the lower-order bitcapacitor 222 and the anode of the PIN diode (the higher-order bitswitch 213 or the lower-order bit switch 223). The other end of thedriving circuit 3 is connected to the switch control unit 45 included inthe control unit 4. The driving circuit 3 outputs DC voltage from theone end based on a control signal output from the switch control unit 45and applies the DC voltage in a forward direction of the PIN diode (thehigher-order bit switch 213 or the lower-order bit switch 223).

The driving circuit 3 includes a high-side switch 31 and a low-sideswitch 32. The high-side switch 31 and the low-side switch 32 aresemiconductor switches, for example, n-type metal-oxide-semiconductorfield-effect transistors (MOSFETs), insulated gate bipolar transistors(IGBTs) or the like.

The source of the high-side switch 31 and the drain of the low-sideswitch 32 are connected in series, and the connection node between thehigh-side switch 31 and the low-side switch 32 as well as the connectionnode between the PIN diode and the higher-order bit capacitor 212 or thelower-order bit capacitor 222 are connected by an electric wire (outputline). The output line is provided with a filter circuit 33 (low-passfilter) constituted by a capacitor FC and a coil FL. Between thehigh-side switch 31 and the connection node of the high-side switch 31and the low-side switch 32, a resistor R and a speed-up capacitor SC areconnected in parallel. The drain of the high-side switch 31 is connectedto the positive output terminal 34 of the driving source (V). The sourceof the low-side switch 32 is connected to the negative output terminal35 of the driving source (V). The respective gate terminals of thehigh-side switch 31 and the low-side switch 32 are connected to twosignal lines extending from the switch control unit 45.

The switch control unit 45 includes the control circuit 451 and thebranch circuit 452, and outputs a control signal for complementaryturning on or off the high-side switch 31 and the low-side switch 32 tosignal lines divided into two branches at the branch circuit 452. Inother words, based on the control signal output from the control circuit451, the branch circuit 452 generates two voltage signals that areopposite to each other between the high level (H) and the low-level (L)to output the one voltage signal to the high-side switch 31 and theother voltage signal to the low-side switch 32. The high-side switch 31to which a high level (H) voltage signal is input is turned to the onstate while the low-side switch 32 to which a low level (L) voltagesignal is input is turned to the off state. Alternatively, the high-sideswitch 31 to which a low level (L) voltage signal is input is turned tothe off state while the low-side switch 32 to which a high level (H)voltage signal is input is turned to the on state. Hence, the high-sideswitch 31 and the low-side switch 32 are complementary controlled so asto be in the on or off state, so that one of the switches is in the onstate while the other is in the off state.

When the high-side switch 31 is in the on state (the low-side switch 32is in the off state), the positive side (V+) of the driving source andthe anode of the PIN diode are connected to each other, so that DCvoltage in the forward direction (voltage necessary for causing currentin the forward direction to flow) is applied to the anode of the PINdiode, turning the PIN diode to the on state. When the high-side switch31 is in the off state (the low-side switch 32 is in the on state), thenegative side (V−) of the driving source and the anode of the PIN diodeare connected to each other, so that negative voltage (voltage in a ragewhere breakdown voltage does not occur) is applied to the anode of thePIN diode, turning the PIN diode to the off state.

FIG. 4 is an illustrative view of the first capacitance element group21. FIG. 5 is an illustrative view of the second capacitance elementgroup 22. In the present embodiment, the first capacitance element group21 of the variable capacitor 2 includes three first capacitance elements211 while the second capacitance element group 22 includes four secondcapacitance elements 221. It is understood that the number of firstcapacitance elements 211 and the number of second capacitance elements221 are not limited to the above-mentioned exemplified numbers.

The capacitances of the higher-order bit capacitors 212 (HCs 1-3) of therespective three first capacitance elements 211 are all the same valueof 16 pF. The higher-order bit capacitors 212 are connected in parallel,so that the total value of the capacitances of the higher-order bitcapacitors 212 for which corresponding higher-order bit switches 213 areturned on is the capacitance of the first capacitance element group 21.It is noted that the same capacitance value does not necessarily meanthat the capacitances are not required to be strictly the same, and amargin of error within the rated value of the capacitor, for example,may be allowed. That is, when the capacitance of the first capacitanceelement group 21 is adjusted, the capacitances of the higher-order bitcapacitors 212 may take the same value within the allowable range interms of precision.

The capacitances of the lower-order bit capacitors 222 (LCs 1-4) of therespective four second capacitance elements 221 are different from eachother in a stepwise manner. Out of these capacitors 222, the lower-orderbit capacitor 222 (hereinafter referred to as the smallest capacitor)with the smallest capacitance has a value of 1 pF, for example.Meanwhile, the capacitances of the other three lower-order bitcapacitors 222 are set to increase in a stepwise manner (in binarysteps) so as to take values obtained by multiplying the capacitance ofthe smallest capacitor by the powers of two. As illustrated in FIG. 5,the lower-order bit capacitors 222 are assigned with the number ofdigits 1 to 4 from the smallest capacitor 222, and the digit numbers areregarded as bit numbers. By combining the on or off state of thelower-order bit capacitors 222 for which capacitances are set in binarysteps, the total value (0 to 15 pF) of the capacitances can be adjustedat 16 levels (two to the fourth power). That is, assuming that thecapacitance of the smallest capacitor is Cmin [pF], and the number oflower-order bit capacitors 222 is n, the capacitance Ck of thelower-order bit capacitor 222 whose digits in number (bit number) is k(here, 1≤K≤n) is represented by a value (Ck=Cmin×2(k−1)) obtained bymultiplying Cmin by 2 to the power of (k−1). The lower-order bitcapacitors 222 are connected in parallel to each other, so that thetotal value of the capacitances of the lower-order bit capacitors 222for which corresponding lower-order bit switches 223 are turned on isthe capacitance of the second capacitance element group 22. Thecapacitances of the lower-order bit capacitors 222 are set in binarysteps, and thus the respective bits are represented by 1 or 0, so thatthe capacitance of the second capacitance element group 22 can beadjusted at each step of 2 to the power of n (n: the number oflower-order bit capacitors 222).

The capacitance of the variable capacitor 2 is the total value of thecapacitance of the first capacitance element group 21 and thecapacitance of the second capacitance element group 22. The capacitanceof a single higher-order bit capacitor 212 is set to a value larger thanthe total value of the capacitances of all the lower-order bitcapacitors 222. Moreover, the capacitance of each of the higher-orderbit capacitors 212, that is, the capacitance of a single higher-orderbit capacitor 212 is set to a value obtained by multiplying thecapacitance of the smallest capacitor by 2 to the power of n (n: thenumber of lower-order bit capacitors 222). The capacitance of thehigher-order bit capacitors 212 and the lower-order bit capacitors 222are thus set, and even if the capacitance required for the variablecapacitor 2 exceeds the total value of the capacitances of all thelower-order bit capacitors 222, this can be addressed by turning thehigher-order bit switch 213 to the on state. In the present embodiment,if the required capacitance is 18 pF, for example, this can be addressedby combining one higher-order bit capacitor 212 (16 pF) and thelower-order bit capacitor 222 (2 pF) corresponding to 2 bits. Thecapacitance of each of the higher-order bit capacitors 212, that is, thecapacitance of a single higher-order bit capacitor 212 is set to a valueobtained by multiplying the capacitance of the smallest capacitor by 2to the power of n (n: the number of lower-order bit capacitors 222).Hence, by combining the higher-order bit capacitors 212 and thelower-order bit capacitors 222, the capacitance of the variablecapacitor 2 can be increased in a stepwise manner. It is noted that thecapacitance of each of the higher-order bit capacitors 212 is requiredto be set to a large value to some extent. An excessive large value,however, may complicate the control, and thus a moderate value is morepreferable.

FIG. 6 is an illustrative view of an update cycle of the semiconductorswitch. The horizontal axis indicates time while the vertical axisindicates a signal waveform corresponding to the update cycle. Theupdate cycle includes a first cycle (t1) and a second cycle (t2). Thefirst cycle (t1) is set to be shorter than the second cycle (t2)(t1<t2).

The control unit 4 updates each of the higher-order bit switches 213with the first cycle (t1) directly after starting impedance matchingoperation. When updating the higher-order bit switch 213, the controlunit 4 outputs a control signal indicating the on or off state of thehigher-order bit switch 213 for every first cycle (t1). As illustratedin FIG. 4, in the case where three higher-order bit switches 213 (HC1,HC2, HC3) are provided, the control signal includes informationindicating the on or off states corresponding to the three higher-orderbit switches 213. For example, in the case where the control signalrepresents “101,” the higher-order bit switch 213 (HC3) is turned on,the higher-order bit switch 213 (HC2) is turned off, and thehigher-order bit switch 213 (HC1) is turned on. Alternatively, in thecase where the control signal represents “000,” all the higher-order bitswitches 213 are turned off, while in the case where the control signalrepresents “111,” all the higher-order bit switches 213 are turned on.During updating with the first cycle (t1), the control unit 4 does notoutput a control signal indicating the on or off state of thelower-order bit switches 223, or continuously outputs a control signalindicating that all the lower-order bit switches 223 are turned on.Accordingly, during updating with the first cycle (t1), the states ofthe lower-order bit switches 223 are fixed. During updating with thefirst cycle (t1), the states of the lower-order bit switches 223 arefixed, which enables reduction in the heat generation due to theswitching loss of the lower-order bit switches 223.

If a control signal previously output and a control signal currentlyoutput are different from each other, the state of any of thehigher-order bit switch 213 is changed from the previous time to thistime. If a control signal previously output and a control signalcurrently output are the same, the states of the higher-order bitswitches 213 remain unchanged from the previous time to this time.

In the case where the load-side impedance is close to a targetedmatching point (for example, the reflection coefficient is less than0.1), the control unit 4 changes the update cycle from the first cycle(t1) to the second cycle (t2). That is, by setting 0.1, for example, asa predetermined value (threshold) for changing the update cycle from thefirst cycle (t1) to the second cycle (t2) based on the reflectioncoefficient, the control unit 4 changes the update cycle to the secondcycle (t2) that is longer than the first cycle (t1) after the load-sideimpedance is close to the targeted matching point.

During updating with the second cycle (t2), the control unit 4 outputscontrol signals indicating the on or off state of the higher-order bitswitches 213 and the lower-order bit switches 223 at every second cycle(t2). Even if update is performed multiple times with the second cycle(t2), the states of the higher-order bit switches 213 are generallymaintained, enabling reduction in the heat generation due to theswitching loss of the higher-order bit switches 213. The second cycle(t2) is longer than the first cycle (t1), and thus the switching countof each of the lower-order bit switches 223 is reduced, enablingreduction in the heat generation due to the switching loss of thelower-order bit switches 223. After the targeted matching point isachieved (for example, the reflection coefficient is less than 0.03),the control unit 4 continues to update the states of the higher-orderbit switches 213 and the lower-order bit switches 223 with the secondcycle (t2).

In the case where the reflection coefficient is equal to or more than apredetermined value (threshold), for example, directly after impedancematching operation is started, impedance matching is performed at theshorter first cycle (t1) by the higher-order bit capacitors 212 havinglarge capacitances, whereby the targeted matching point can be achievedin a short time period while the heat generation of the lower-order bitswitches 223 is reduced. In the case where the reflection coefficient isless than the predetermined value (threshold), the load-side impedanceis in a near-matched state, and thus the states of the higher-order bitswitches 213 are scarcely changed and are maintained, which lessens theinfluence of the heat generation due to the switching of thehigher-order bit switches 213. It is noted that in the case where thereflection coefficient is equal to or more than the predetermined value(threshold), the higher-order bit switches 213 are updated with thefirst cycle (t1) while the states of the respective lower-order bitswitches 223 are fixed, though the states of the switches are notlimited thereto. Even in the case where the reflection coefficient isequal to or more than the predetermined value (threshold), thehigher-order bit switches 213 and the lower-order bit switches 223 maybe updated with the first cycle (t1). In the case where the reflectioncoefficient is equal to or more than the predetermined value(threshold), i.e., in an impedance mismatched state, rough adjustmentsare preferentially performed, and thus the higher-order bit switches 213are mainly changed to allow the load-side impedance to be close to thematching point in a relatively short time period, making the reflectioncoefficient less than the predetermined value (threshold). Hence, evenif the states of the lower-order bit switches 223 are updated with thefirst cycle (t1), the influence of the heat generation can be lessened.

FIG. 7 is a flowchart illustrating processing performed by the controlunit 4 according to Embodiment 1. The control unit 4 of the impedancematching device 1 starts impedance matching operation in response to amatching operation starting instruction, or the like.

The control unit 4 turns the lower-order bit switch 223 off (S11). Thecontrol unit 4 turns all the lower-order bit switches 223 of the secondcapacitance element group 22 included in the variable capacitor 2 to theoff state. All the lower-order bit switches 223 are turned to the offstate to thereby disable all the lower-order bit capacitors 222 of thesecond capacitance element group 22, resulting in 0 pF of thecapacitance of the second capacitance element group. By turning all thelower-order bit switches 223 to the off state, the heat generation ofthe lower-order bit switches 223 can be reduced. It is noted that allthe lower-order bit switches 223 may be turned to another state, notturned to the off state. For example, the states of the lower-order bitswitches 223 at a time when the previous impedance matching operationwas completed are stored, and the stored states may be employed.

The control unit 4 sets the update cycle to the first cycle (S12). Thecontrol unit 4 refers to the first cycle stored in advance in thestorage unit 40 and sets the first cycle as an update cycle. Theprocessing at step S16, which will be described later, is performed atthis first update cycle.

The control unit 4 obtains information concerning an impedance, andcalculates (derives) an impedance and a reflection coefficient (S13).

The control unit 4 obtains information (parameters) concerning theimpedance viewed from the high-frequency power source 6 toward the load8 side that is detected and output by the high-frequency detection unit7, and calculates an impedance viewed from the high-frequency powersource 6 toward the load 8 side as a load-side impedance. Furthermore,the control unit 4 calculates (derives) a reflection coefficient basedon the parameters.

The control unit 4 calculates a capacitance (S14). The control unit 4calculates the capacitance required for the variable capacitor 2 inorder to match the calculated load-side impedance to the outputimpedance of the high-frequency power source 6.

The control unit 4 decides a targeted state of the switches (S15). Thecontrol unit 4 decides the on or off state of the higher-order bitswitches 213 and the lower-order bit switches 223 included in thevariable capacitor 2 as a targeted state of the switches in order tomatch the capacitance of the variable capacitor 2 to the capacitancecalculated by the capacitance calculation unit 42. Alternatively, thecontrol unit 4 may decide the on or off state of only the higher-orderbit switches 213.

The control unit 4 updates the states of the higher-order bit switches213 (S16). The control unit 4 extracts the states of the higher-orderbit switches 213 in the targeted state of the switches decided andupdates the on or off state of the higher-order bit switches 213 withthe first cycle. The control unit 4 stores the updated on or off stateof the higher-order bit switches 213 in the storage unit 40 inassociation with the time point when updating is performed.

The control unit 4 determines whether or not the reflection coefficientis less than a predetermined value (S17). The control unit 4 comparesthe reflection coefficient (the current reflection coefficient)calculated at step S13 and the predetermined value for the reflectioncoefficient stored in the storage unit 40 in advance, and determineswhether or not the current reflection coefficient is less than thepredetermined value. The predetermined value for the reflectioncoefficient is, for example, 0.1. By setting the reflection coefficientto 0.1, this can be used as a threshold for determining whether or not amatched-state is almost achieved.

If the reflection coefficient is not less than the predetermined value(S17: No), that is, if the reflection coefficient is equal to or morethan the predetermined value, the control unit 4 performs loopprocessing in order to execute the processing from step S13 again.Accordingly, updating with the first cycle is continued.

If the reflection coefficient is less than the predetermined value (S17:Yes), the control unit 4 sets the update cycle to the second cycle(S18). The control unit 4 refers to the second cycle stored in advancein the storage unit 40 and sets the second cycle as an update cycle. Theprocessing at step S22, which will be described later, is performed withthe second cycle. The second cycle is an cycle longer than the firstcycle. By setting the second cycle to an cycle two-times longer than thefirst cycle, for example, the switching count upon updating can bereduced, which enables efficient reduction in heat generation.

The control unit 4 performs processing from S19 to S21 similarly to theprocessing from S13 to S15. It is noted that in the processing at S21,the control unit 4 decides the states of the higher-order bit switches213 and the lower-order bit switches 223 as a targeted state of theswitches.

The control unit 4 updates the states of the higher-order bit switches213 and the lower-order bit switches 223 (S22). The control unit 4updates the on or off state of the higher-order bit switches 213 and thelower-order bit switches 223 with the second cycle based on the decidedtargeted state of the switches. The control unit 4 stores the updated onor off state of the higher-order bit switches 213 and the lower-orderbit switches 223 in the storage unit 40 in association with the timepoint of updating.

The control unit 4 determines whether or not the reflection coefficientis less than the predetermined value (S23). Similarly to the processingat step S17, the control unit 4 compares the reflection coefficient (thecurrent reflection coefficient) calculated at step S19 and thepredetermined value for the reflection coefficient stored in the storageunit 40 in advance, and determines whether or not the current reflectioncoefficient is less than the predetermined value.

As described above, the total value (15 pF, for example) of thecapacitances of all the lower-order bit capacitors 222 is smaller thanthe capacitance (16 pF, for example) of a single higher-order bitcapacitor 212. Accordingly, if the required capacitance of the variablecapacitor 2 varies from, for example, 31 pF to 32 pF upon one updating,the number of higher-order bit switches 213 that are to be turned on isincreased from one to two, and the lower-order bit switches 223 that areall in the on state are all turned to the off state. Such a phenomenonin which one higher-order bit switch 213 changes its state is calledcarrying (or borrowing). That is, the state of one higher-order bitswitch 213 is changed for one updating, however, the amount of change inthe required capacitance of the variable capacitor 2 is a small value,and the load-side impedance is close to the matching point. In contrastthereto, in the case where the states of two or more higher-order bitswitches 213 are changed, the amount of change in the requiredcapacitance of the variable capacitor 2 is a large value, and theload-side impedance is away from the matching point. When it isdetermined whether or not the load-side impedance achieves a matchedstate once and changes to an unmatched state again (a state where theload-side impedance is away from the matching point) by carrying orborrowing, the capacitances of the multiple higher-order bit capacitors212 in the first capacitance element group 21 are set to the same valuesas described above.

If the reflection coefficient is not less than the predetermined value(S23: NO), the control unit 4 performs loop processing in order toexecute the processing at step S12 again. Accordingly, the update cycleis changed to the first cycle to update the higher-order bit switches213. If the reflection coefficient is not less than the predeterminedvalue, that is, if the reflection coefficient is equal to or more thanthe predetermined value, the load-side impedance is away from thematching point (in a mismatched state), rough adjustments arepreferentially performed, and the impedance is adjusted by thehigher-order bit switches 213 (first capacitance element group 21). Inother words, the control unit 4 sets (returns) the update cycle to thefirst cycle with a shorter update cycle to fix the states of thelower-order bit switches 223 as well as to update the states of thehigher-order bit switches 213, which allows the load-side impedance tobe close to the matching point soon by the higher-order bit capacitors212 with large capacitance. During updating with the first cycle, thestates of the lower-order bit switches 223 are fixed (maintained), whicheliminates the switching loss of the lower-order bit switches 223,enabling reduction in the heat generation.

If the reflection coefficient is less than the predetermined value (S23:Yes), the control unit 4 performs loop processing in order to executethe processing at step S19 again. Thus, updating with the second cycleis continued.

In the present embodiment, the update cycle is changed depending onwhether or not the reflection coefficient is less than the predeterminedvalue, though the basis for change is not limited thereto. The controlunit 4 may change the update cycle depending on whether or not reflectedpower, reflected voltage or reflected current is less than apredetermined value. The smaller the reflection coefficient is, thesmaller the reflected power, reflected voltage or reflected current is.Thus, the control unit 4 may perform an update with the second cycle ifthe reflected power, reflected voltage or reflected current is less thanthe predetermined value while performing an update with the first cycleif the reflected power, reflected voltage or reflected current is equalto or more than the predetermined value.

Modification 1

FIG. 8 is a circuit diagram roughly illustrating one example of theconfiguration of a driving circuit 3 according to Modification 1. It isnoted that FIG. 8 mainly illustrates the first capacitance element 211.In Embodiment 1, the control circuit 451 outputs respective two voltagesignals that are opposite to each other to the high-side switch 31 andthe low-side switch 32, though the signals to be output are not limitedthereto. The control circuit 451 may be configured to output a voltagesignal (common input signal) common to the high-side switch 31 and thelow-side switch 32.

The driving circuit 3 in Modification 1 is provided with a high-sideswitch 31 and a low-side switch 32 similarly to the driving circuit 3 inEmbodiment 1. The high-side switch 31 is constituted by a photocoupler.The low-side switch 32 is constituted by an n-type MOSEFT similarly toEmbodiment 1.

Similarly to Embodiment 1, the emitter of the high-side switch(photocoupler) 31 is connected in series to the drain of the low-sideswitch 32, and the connection node between the high-side switch(photocoupler) 31 and the low-side switch 32 is connected to theconnection node between a higher-order bit capacitor 212 or alower-order bit capacitor 222 and a PIN diode (a higher-order bit switch213 or a lower-order bit switch 223) by a connection line (output line).The output line is provided with a filter circuit 33 (low-pass filter)constituted by a capacitor FC and a coil FL.

Similarly to Embodiment 1, the collector of the high-side switch(photocoupler) 31 is connected to the positive output terminal 34 of adriving source (V) while the source of the low-side switch (FET) 32 isconnected to the negative output terminal 35 of the driving source (V).

The anode of the photodiode of the high-side switch (photocoupler) 31 isconnected to a 5-V DC power source, for example, while the cathodethereof is connected to the gate of the low-side switch (FET) 32.

The control circuit 451 included in a switch control unit 45 and theconnection node between the cathode of the photodiode and the gate ofthe low-side switch (FET) 32 are connected by a signal line. The switchcontrol unit 45 outputs a voltage signal (5 V or larger, for example)larger than the output voltage of the DC power source connected to thephotodiode as a voltage signal at the high level (H) to thereby turn thehigh-side switch (photocoupler) 31 to the off state and turn thelow-side switch (FET) 32 to the on state. The switch control unit 45outputs a voltage signal of 0 V as a voltage signal at the low level (L)to thereby turn the high-side switch (photocoupler) 31 to the on stateand the low-side switch (FET) 32 to the off state.

The high-side switch (photocoupler) 31 is turned to the on state tothereby turn the PIN diode to the on state. The low-side switch (FET) 32is turned to the on state to thereby turn the PIN diode to the offstate.

In Modification 1 and Embodiment 1 illustrated in FIG. 3, the anode ofthe PIN diode (the higher-order bit switch 213 or the lower-order bitswitch 223) is connected to the higher-order bit capacitor 212 or thelower-order bit capacitor 222 while the cathode thereof is grounded(connected to the ground), though the configuration of the PIN diode isnot limited thereto. The anode of the PIN diode (the higher-order bitswitch 213 or the lower-order bit switch 223) may be grounded while thecathode thereof may be connected to the higher-order bit capacitor 212or the lower-order bit capacitor 222. Here, in the case where thepositive side (V+) of the driving source is connected to the connectionnode (cathode of the PIN diode) between the PIN diode and thehigher-order bit capacitor 212 or the lower-order bit capacitor 222 (thehigh-side switch 31 is in the on state and the low-side switch 32 is inthe off state), the PIN diode is turned off. In the case where thenegative side (V−) of the driving source is connected to the cathode ofthe PIN diode (the high-side switch 31 is in the off state and thelow-side switch 32 is in the on state), the PIN diode is turned on.

Hence, a common input signal being the same voltage signal is outputfrom the control circuit 451 to the high-side switch (photocoupler) 31and the low-side switch 32 through one signal line, whereby thehigh-side switch (photocoupler) 31 and the low-side switch 32 cancomplementary be controlled between on and off. A common input signal isoutput from the control circuit 451 through one signal line, whicheliminates the need for the branch circuit 452 in Embodiment 1.

It is to be understood that the embodiments disclosed here isillustrative in all respects and not restrictive. The scope of thepresent invention is defined by the appended claims, and all changesthat fall within the meanings and the bounds of the claims, orequivalence of such meanings and bounds are intended to be embraced bythe claims.

It is to be noted that, as used herein and in the appended claims, thesingular forms “a”, “an”, and “the” include plural referents unless thecontext clearly dictates otherwise.

It is to be noted that the disclosed embodiment is illustrative and notrestrictive in all aspects. The scope of the present invention isdefined by the appended claims rather than by the description precedingthem, and all changes that fall within metes and bounds of the claims,or equivalence of such metes and bounds thereof are therefore intendedto be embraced by the claims

What is claimed is:
 1. An impedance matching device that is providedbetween a high-frequency power source and a load and that obtainsinformation concerning an impedance viewed from an output terminal ofthe high-frequency power source or from an equivalent to the outputterminal toward a load side to achieve impedance matching between thehigh-frequency power source and the load, comprising: a variablecapacitor including a plurality of capacitance elements respectivelyhaving capacitor each having one end connected to the high-frequencypower source and semiconductor switch connected in series to thecapacitor, the plurality of capacitance elements being connected inparallel; and a control unit that controls an on or off state of theeach of semiconductor switches such that an impedance of thehigh-frequency power source is matched to an impedance of the load basedon the information concerning the impedance obtained, wherein thecontrol unit derives a reflection coefficient based on the informationobtained concerning the impedance viewed from the high-frequency powersource toward the load side, updates states of the respectivesemiconductor switches included in the plurality of capacitance elementswith a first cycle in a case where the reflection coefficient is equalto or more than a predetermined value, and updates states of therespective semiconductor switches included in the plurality ofcapacitance elements with a second cycle longer than the first cycle ina case where the reflection coefficient is less than the predeterminedvalue.
 2. The impedance matching device according to claim 1, whereinthe predetermined value for the reflection coefficient is 0.1.
 3. Theimpedance matching device according to claim 1, wherein the plurality ofcapacitance elements include a first capacitance element group and asecond capacitance element group that includes the capacitors eachhaving a capacitance smaller than a capacitance of one of the capacitorsconstituting the first capacitance element group, wherein the controlunit updates states of the semiconductor switches included in the firstcapacitance element group and maintains states of the semiconductorswitches included in the second capacitance element group at a time ofupdating with the first cycle, and updates states of the semiconductorswitches included in the first capacitance element group and thesemiconductor switches included in the second capacitance element groupat a time of updating with the second cycle.
 4. The impedance matchingdevice according to claim 3, wherein a capacitance of any one of thecapacitors included in the first capacitance element group is largerthan a total value of capacitances of all the capacitors included in thesecond capacitance element group.
 5. An impedance matching methodachieving impedance matching between a high-frequency power source and aload by a variable capacitor provided between the high-frequency powersource and the load, the variable capacitor including a plurality ofcapacitance elements respectively having a capacitor and a semiconductorswitch, the method comprising: deriving a reflection coefficient basedon information obtained concerning an impedance viewed from thehigh-frequency power source toward a load side; updating states of therespective semiconductor switches included in the plurality ofcapacitance elements with a first cycle in a case where the reflectioncoefficient is equal to or more than a predetermined value; and updatingstates of the respective semiconductor switches included in theplurality of capacitance elements with a second cycle longer than thefirst cycle in a case where the reflection coefficient is less than thepredetermined value.